I Introduction
Line spectrum estimation (LSE) is a fundamental problem in statistical signal processing due to its widespread application in channel estimation [1] and direction of arrival (DOA) estimation [2]. On the one hand, many classical methods have been proposed, such as periodogram, MUSIC and ESPRIT [3, 4, 5]. On the other hand, sparse representation and compressed sensing (CS) based methods have been proposed to estimate frequencies for multiple sinusoids. At first, grid based method where the continuous frequency is discretized into a finite set of grid points is proposed [6]. It is shown that grid based method will incur basis mismatch when the true frequencies do not lie exactly on the grid [7]. As a result, off-the-grid compressed sensing methods have been proposed, such as atom norm minimization and gridless SPICE (GLS) [9, 10, 8, 11, 12]. The atomic norm-based methods involve solving a semidefinite programming (SDP) problem [13], whose computation complexity is prohibitively high for large problem sizes. In [14], a Newtonalized orthogonal matching pursuit (NOMP) method is proposed, where a Newton step and feedback are utilized to refine the frequency estimates. Compared to the incremental step in updating the frequencies in NOMP approach, the iterative reweighted approach (IRA) [15] estimates the frequencies in parallel, which improves the estimation accuracy at the cost of increasing complexity. In [16], superfast LSE methods are proposed based on fast Toeplitz matrix inversion algorithm. In [17]
, an off-grid based variational line spectrum estimation (VALSE) algorithm is proposed, where posterior probability density function (PDF) of the frequency is provided. In
[18], the VALSE is extended to the MMV setting, and it shows the relationship between the VALSE for the SMV and the VALSE for the MMV.Recently, the mmWave multiple input multiple output (MIMO) system has drawn a great deal of attention. Since the mmWave accompanies large bandwidths, the cost and power consumption are huge due to high precision (e.g., 10-12 bits) analog-to-digital converters (ADCs) [19]. Consequently, low precision ADCs are adopted to alleviate the ADC bottleneck. Another motivation is wideband spectrum sensing in bandwidth-constrained wireless networks [20, 21]. In order to reduce the communication overhead, the sensors quantize their measurements even into a single bit, and the spectrum has to be estimated from the quantized measurements at the fusion center (FC). Thus designing recovery algorithms under low precision quantized observations is meaningful [28, 29].
The most related work to ours is [23], where LSE from heavy quantizations of their noisy complex-valued random linear measurements has been studied. The Cramér-Rao bound is derived and an atomic norm soft thresholding based algorithm has been proposed [23]. While in this paper, we study the LSE from one-bit quantization of their noisy measurements. Utilizing the expectation propagation (EP) principle [24], the generalized linear model can be iteratively decomposed as two modules (a standard linear model and a componentwise minimum mean square error (MMSE) module) [25]. Thus we run the VALSE algorithm in the standard linear module where the frequency estimate is iteratively refined. For the MMSE module, it refines the pseudo observations of the linear model ^{1}^{1}1Iteratively approximating the generalized linear model as a standard linear model is very beneficial, as many well developed methods such as the information-theoretically optimal successive interference cancellation (SIC) is developed in the SLM.. By iterating between the two modules, it improves the frequency estimation gradually. Finally, numerical experiments are conducted to demonstrate the effectiveness of the proposed algorithm.
Ii Problem Setup
Let be a line spectrum signal consisting of complex sinusoids
(1) |
where is the complex amplitude of the th frequency, is the th frequency, and
(2) |
The line spectrum signal is corrupted by the additive white Gaussian noise (AWGN), and are quantized into a single bit, which can be expressed as
(3) |
where ,
is the variance of the noise, and
returns the sign of the variables. Note that the knowledge of the variance of the noise has no effect on the frequency estimation, as revealed in [26], while its value does have. The goal in this paper is to recover the set of frequencies and the corresponding coefficients without knowing the sparsity level .Since we usually do not know the sparsity level , we adopt the following model where we assume that the line spectrum signal consisting of complex sinusoids [17]
(4) |
where and is usually known and satisfies . Since the number of frequencies is , we introduce the binary hidden variables , and means that the th frequency is active, otherwise deactive (). The probability mass function of is
(5) |
Given that , we assume that ^{2}^{2}2Sometimes we use
instead when the random variable is clear from the text.
. Thusfollows a Bernoulli-Gaussian distribution, that is
(6) |
From (5) and (6), it can be seen that the parameter denotes the probability of the th component being active and is a variance parameter. The variable has the prior PDF . Without any knowledge of the frequency , the uninformative prior distribution is used [17]. For encoding the prior distribution, please refer to [17, 18] for further details.
Given , the probability density function of can be easily calculated through (3). According to the Bayes rule, the joint PDF is
(7) |
where denotes the model parameters. Directly maximizing over and the nusiance parameters is intractable. As a result, an iterative algorithm is designed in the following section.
Iii Algorithm
At first, we present the factor graph and the algorithm module as shown in Fig. 1. Specifically, in the -th iteration, from the EP point of view, the message transmitted from the factor node to the variable node is projected as a Gaussian distribution, i.e., the message is projected as . According to the EP, in the -th iteration can be viewed as the prior distribution of . Combing the likelihood , we projected the posterior as Gaussian distribution using the EP, i.e., we obtain the component-wise MMSE estimate of ,
(8) | |||
(9) |
here the expectation and variance are taken with respect to the posterior PDF , and the analytic expression can be obtained [27]. Now the posterior PDF of is approximated as
(10) |
Then we calculate the message from the variable node to the factor node as
(11) |
and and can be calculated as
(12a) | |||
(12b) |
where denotes componentwise multiplication. From the definition of the factor node , we obtain a pseudo linear observation model
(13) |
where , and . In [17]
, the VALSE is derived where the additive Gaussian noise is homogenous while here the additive Gaussian noise is heteroscedastic (independent components having different variance). We can average the noise variance but it incurs some performance degradation in our numerical experiments. As a result, some minor modifications are needed to ensure that the original VALSE works. Due to space limitations, we do not present the details about deriving the VALSE for model (
13).Now we run the VALSE algorithm. Let be the set of indices of the non-zero components of , i.e., . Similarly, define as the estimate of
by the VALSE algorithm. Note that the VALSE is only initialized using Heuristic
in the first iteration, i.e., . The VALSE algorithm is stopped when the support estimate is kept unchanged. Then we calculate the posterior means and variances of through the posterior PDF of and as(14) | |||
(15) |
where , and are the posterior means and covariance of . We set and we calculate the extrinsic and variance given by
(16) | |||
(17) |
and we input them to module B. The algorithm iterates until convergence or the maximum number of iterations is reached. The VALSE-EP algorithm is summarized as Algorithm 1.
Iii-a Computation complexity
In [17], it shows that the complexity per iteration is dominated by the two steps: the maximization of and the approximations of the posterior PDF by mixtures of von Mises pdfs, and the complexity of the two steps are and with Heuristic in [17]. For the VALSE-EP algorithm, in each inner iteration where VALSE is performed, the posterior covariance matrix of has to be calculated, whose computation complexity is at most because . For a single iteration, the computation complexity of VALSE-EP is , whereas the computation complexity of the atomic norm based algorithm is [12].
Iii-B Extension to the MMV case
The extension to the multisnapshot scenario is straightforward. For the MMV case, the model can be described as
(18) |
where and denotes the number of snapshots. The algorithm can be designed by iterating between the two modules. Performing the MMSE operation is straightforward. For module A, it can be decoupled as SMVs
(19) |
where , and . In [18, the end of Sec. IV], the relationship of the VALSE algorithm between the SMVs and MMVs has been revealed. For the th snapshot, we perform the VALSE algorithm and obtain for the -th frequency. Then is obtained via summing for all the snapshots, i.e., , and now each is updated as . We use to obtain estimates and . In addition, we update the weight and their covariance by applying the SMV VALSE. Let and be the estimated weight and their covariance of the th snapshot. For updating , can be viewed as a sum of the results for each snapshots. Let denote the estimate of the th SMV VALSE, then model parameters estimates is updated as the average of their respective estimates, i.e., . Besides, can be naturally estimated as .
Here a illustrative example is presented where , dB for each snapshot, and the single true frequency is . The VALSE-EP outputs the posterior PDF of the frequency, as shown in Fig. 2. It can be seen that the PDF is very peaked, and increasing the number of snapshots makes the posterior PDF more concentrated, which means that the uncertain degrees is reduced.
Iv Numerical Simulation
In this section, numerical experiments are conducted to verify the proposed algorithm. We evaluate the signal estimation error, frequency estimation error, the correct model order estimation probability under one-bit quantization. To generate the real signal, we will replace in (4) with true complex sinusoids . The frequencies are randomly drawn such that the minimum wrap around distance is greater than . We evaluate the performance of the VALSE algorithm utilizing noninformative prior, i.e., . The magnitudes of the weight coefficients are drawn i.i.d. from a Gaussian distribution
, and the phases are drawn i.i.d. from a uniform distribution between
. We define the signal to noise ratio (SNR) as for the SMV case, while for the MMVs we fix the SNR for each snapshot. We define the normalized MSE (NMSE) of signal (for unquantized system) and as and , respectively. For one-bit quantization, we calculate the debiased NMSE of the signal for single and multi snapshots defined as or . As for the frequency estimation error, we average only the trials in which all those algorithms estimate the correct model order. The Algorithm 2 stops when the number of iterations exceeds . All the results are averaged over Monte Carlo (MC) trials. The CRB of the frequency estimation for unquantized samples [22] and one-bit samples [23] are also evaluated. We define the empirical which represents the probability of correct model order estimation.Iv-a Estimation by varying
We examine the performance of the VALSE-EP by varying the number of measurements . The results are shown in Fig. 3. It can be seen that both the debiased NMSE of the signal and frequency decreases as the number of measurements increases. In addition, the frequency estimation error of the VALSE is lower than the CRB, which still makes sense because VALSE is the Bayesian method. Compared to the single snapshot, utilizing the multi snapshot increases the performance. Overall, the correct model order probability increases as the number of measurements increases, and has a slightly fluctuation when the number of measurements exceeds .
Iv-B Estimating by varying the snapshots
The performance of the VALSE-EP is investigated with varied . The results are shown in Fig. 4. It can be seen that as the number of snapshots increases, the NMSE of the signal decreases and becomes stable. In addition, the performance of the VALSE-EP is better for dB than that of dB. The NMSE of the frequency decreases as the number of snapshots increases. As for the correct model order probability, the overall trend is upwards as the number of snapshots increases.
V Conclusion
In this paper, a VALSE-EP algorithm is proposed to deal with the LSE problem from one-bit quantized samples. The VALSE-EP is an off-grid algorithm which iteratively refines the frequency estimates. Besides, the VALSE-EP is extended to deal with the MMVs. Finally, numerical results show the effectiveness of the VALSE-EP.
References
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