High-Rate Convolutional Codes with CRC-Aided List Decoding for Short Blocklengths

11/15/2021
by   Wenhui Sui, et al.
0

Recently, rate-1/ω zero-terminated and tail-biting convolutional codes (ZTCCs and TBCCs) with cyclic-redundancy-check (CRC)-aided list decoding have been shown to closely approach the random-coding union (RCU) bound for short blocklengths. This paper designs CRCs for rate-(ω-1)/ω CCs with short blocklengths, considering both the ZT and TB cases. The CRC design seeks to optimize the frame error rate (FER) performance of the code resulting from the concatenation of the CRC and the CC. Utilization of the dual trellis proposed by Yamada et al. lowers the complexity of CRC-aided serial list Viterbi decoding (SLVD) of ZTCCs and TBCCs. CRC-aided SLVD of the TBCCs closely approaches the RCU bound at a blocklength of 128.

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I Introduction

The structure of concatenating a convolutional code (CC) with a cyclic redundancy check (CRC) code has been a popular paradigm since 1994 when it was proposed in the context of hybrid automatic repeat request (ARQ) [13]. It was subsequently adopted in the cellular communication standards of both 3G [17] and 4G LTE [10]. In general, the CRC code serves as an outer error-detecting code that verifies if a codeword has been correctly received, whereas the CC serves as an inner error-correcting code to combat channel errors.

Recently, there has been a renewed interest in designing powerful short blocklength codes. This renewed interest is mainly driven by the development of finite blocklength information theory by Polyanskiy et al., [12] and the stringent requirement of ultra-reliable low-latency communication (URLLC) for mission-critical IoT (Internet of Things) service [5]. In [12], Polyanskiy et al.

developed new achievability bound known as the random-coding union (RCU) bound and new converse bound, known as the meta-converse (MC) bound. Together, these two bounds characterize the error probability of the best short blocklength code of length

with codewords. The URLLC for mission-critical IoT requires that the time-to-transmit latency is within 500 while maintaining a block error rate no greater than .

Several short blocklength code designs have been proposed in literature. Important examples include the tail-biting (TB) convolutional codes decoded using the wrap-around Viterbi algorithm (WAVA) [4], extended BCH codes under ordered statistics decoding [2, 20], non-binary low-density parity-check (LDPC) codes [3], non-binary turbo codes [9], and polar codes under CRC-aided successive-cancellation list decoding [16]. Recent advances also include the polarization adjusted convolutional codes by Arıkan[1]. As a comprehensive overview, Coşkun et al. [2] surveyed most of the contemporary short blocklength code designs in recent decade. We refer the reader to [2] for additional information.

In [19], Yang et al. proposed the CRC-aided CCs as a powerful short blocklength code for binary-input (BI) additive white Gaussian noise (AWGN) channels. In [19], the convolutional encoder of interest is of rate- and is either zero-terminated (ZT) or TB. In order to construct a good CRC-aided CC, Yang et al. designed a distance-spectrum optimal (DSO) CRC generator polynomial for the given CC. The resulting concatenated code generated by the DSO CRC polynomial and the convolutional encoder is a good CRC-aided CC.

The nature of the concatenation naturally permits the use of the serial list Viterbi decoding (SLVD), an efficient algorithm originally proposed by Seshadri and Sundberg [15]. Yang et al. showed that the expected list rank of the SLVD of the CRC-aided CC is small at a target low error probability, thus achieving a low average decoding complexity. Yang et al. demonstrated that several concatenated codes generated by the DSO CRC polynomial and the TBCC, or in short, CRC-TBCCs, approach the RCU bound. In [14], Schiavone extended this line of work by looking at the parallel list Viterbi decoding with a bounded list size. However, these works did not consider rate- CCs. It remains open as to whether this framework can be extended to CCs with arbitrary rate such that the resulting concatenated code can approach the RCU bound at a low decoding complexity.

In this paper, we consider designing good CRC-aided CCs for rate- CCs at short blocklength for the BI-AWGN channel, where the CC is either ZT or TB. We consider systematic, rate- convolutional encoders. The resulting concatenated codes are respectively called a CRC-ZTCC and CRC-TBCC. We assume that the SLVD has a sufficiently large list size such that no negative acknowledgement is produced. Thus, the SLVD is an implementation of maximum-likelihood decoding. The frame error rate (FER) is in fact the undetected error probability. Simulations show that in the short-blocklength regime, our rate- CRC-TBCCs still perform closely to the RCU bound.

A work related to this line of research is that of Karimzadeh & Vu [6]. They considered designing the optimal CRC polynomial for multi-input CCs. In their framework, the information sequence is first divided into streams, one for each input rail and they aim at designing optimal CRC polynomial for each rail. Unlike their architecture, in this paper, the information sequence is first encoded with a single CRC polynomial and is then divided into streams. Simulation results show that our framework can yield better FER performance than that of Karimzadeh & Vu.

For rate- CCs, the SLVD on the primal trellis requires high decoding complexity because of the outgoing branches at each node. SLVD implementation becomes more complicated when there are more than two outgoing branches per state. In order to simplify SLVD implementation and reduce complexity, we utilize the dual trellis pioneered by Yamada et al.[18]. The dual trellis expands the length of the primal trellis by a factor of , while reducing the number of outgoing branches at each node from to at most two.

The remainder of this paper is organized as follows. Section II reviews systematic encoding for convolutional codes and describes the dual trellis construction. Section III considers CRC-ZTCCs for rate- CCs. It addresses the zero-termination issue, presents DSO CRC design for high-rate ZTCCs, and shows CRC-ZTCC simulation results. Section IV considers CRC-TBCCs for rate- CCs. It addresses how to find the tail-biting initial state over the dual trellis, describes DSO CRC design for TBCCs, and shows CRC-TBCC simulation results. Section V concludes the paper.

Notation: Let and denote the information length and blocklength in bits. Let denote the rate of the CRC-aided CC. A degree- CRC polynomial is of the form , where , . For brevity, a CRC polynomial is represented in hexadecimal when its binary coefficients are written from the highest to lowest order. For instance, 0xD represents . The codewords are BPSK modulated. The SNR is defined as (dB), where represents the BPSK amplitude and the noise is always distributed as a standard normal.

Ii Systematic Encoding and Dual Trellis

This section describes systematic encoding and introduces the dual trellis proposed by Yamada et al. [18] for convolutional codes with rate , where represents the overall constraint length.

Ii-a Systematic Encoding

We briefly follow [8, Chapter 11] in describing a systematic convolutional encoder. A systematic convolutional encoder is represented by its parity check matrix

(1)

where each is a polynomial of degree up to in delay element associated with the -th code stream, i.e.,

(2)

where . For convenience, we represent each in octal form. For instance, can be concisely written as . Define , . The systematic encoding matrix associated with is given by

(3)

The first output bit is a coded bit whereas the remaining output bits are a direct copy of the corresponding input bits.

Ii-B Dual Trellis

The primal trellis associated with an ZTCC has outgoing branches per state. In the case where , SLVD over the primal trellis will become complicated. In [19], the low decoding complexity of SLVD for rate- convolutional codes relies on the fact that only outgoing branches are associated with each state. In order to efficiently perform SLVD, we consider the dual trellis proposed by Yamada et al. [18].

We briefly explain the dual trellis construction for parity check matrix . First, define the maximum instant response order as

(4)

The state of the dual trellis is represented by the partial sums of adders in the observer canonical form of . At time index , , the state is given by

(5)

Next, we show how state evolves in terms of the output bits , , so that a dual trellis can be established.

Dual trellis construction for :

  • At time , , where . Namely, only states exist at .

  • At time , , draw branches from each state to state by

    (6)
  • At time , draw branches from each state to state by

    (7)

    where .

  • For time , draw a branch from each state according to (6) only for .

After repeating the above construction for each , , we obtain the dual trellis associated with the convolutional code. Since the primal trellis is of length , whereas the dual trellis is of length , dual trellis can be thought of as expanding the primal trellis length by a factor of , while reducing the number of outgoing branches per state from to no greater than .

Iii ZTCC with DSO CRC via Dual Trellis SLVD

This section considers CRC-ZTCCs for rate- CCs. Section III-A presents a zero termination method over the dual trellis. Section III-B describes our DSO CRC polynomial search procedure. Finally, Section III-C presents simulation results of the CRC-ZTCC compared with the RCU bound. As a case study, this paper mainly focuses on the rate- systematic feedback convolutional codes in [8, Table 12.1(e)].

1-61.2
DSO CRC
0x9
0x4D
0x31B
0x9
0x7B
0x3F1
1-61.2
TABLE I: DSO CRC Polynomials for rate- ZTCC at Blocklength Generated by With and by With

Iii-a Zero Termination of Dual Trellis

For an CC, zero termination over the dual trellis requires at most steps. In our implementation, a breadth-first search identifies the zero-termination input and output bit patterns that provide a trajectory from each possible state to the zero state. The input and output bit patterns have lengths and respectively.

Iii-B Design of DSO CRCs for High-Rate ZTCCs

In general, a DSO CRC polynomial provides the optimal distance spectrum which minimizes the union bound on the FER at a specified SNR [19]. In this paper, we focus on the low FER regime. Thus, the DSO CRC polynomials identified in this paper simply maximize the minimum distance of the concatenated code. Examples in [19] indicate that DSO CRC polynomials designed in this way can provide optimal or near-optimal performance for a wide range of SNRs.

The design procedure of the DSO CRC polynomial for high-rate ZTCCs essentially follows from the DSO CRC design algorithm for low target error probability in [19]. The first step is to collect the irreducible error events (IEEs), which are ZT paths on the trellis that deviate from the zero state once and rejoin it once. In order to maintain efficiency, we only consider IEEs with output Hamming weight up to some threshold . Dynamic programming constructs all ZT paths of length equal to and output weight no greater than . Finally, we use the resulting set of ZT paths to identify the degree- DSO CRC polynomial for the rate- CC.

Fig. 1: FER vs. SNR for various CRC-ZTCCs. The ZTCC is generated with the encoder . The DSO CRC polynomials with degrees and are 0x9, 0x7B, and 0x3F1, respectively. Values in parenthesis denote information length and blocklength , respectively.

Table I presents the DSO CRC polynomials for ZTCCs generated with and . The design assumes a fixed blocklength bits. Due to the overhead caused by the CRC bits and by zero termination, the rates of CRC-ZTCCs are less than . Specifically, for a given information length , CRC degree and an encoder, the blocklength for a CRC-ZTCC is given by

(8)

yielding a rate

(9)

We see from (8) that the convolutional encoder can accept any CRC degree as long as is divisible by .

Iii-C Results and Comparison with RCU Bound

Fig. 1 shows the performance of CRC-ZTCCs with increasing CRC degrees and and a fixed blocklength bits. We see that at the target FER of , increasing the CRC degree reduces the gap to the RCU bound. With and , the CRC-ZTCC approaches the RCU bound within dB.

Fig. 2: FER vs. SNR for CRC-ZTCCs designed under Karimzadeh et al.’s scheme [6] and our scheme. Both CRC-ZTCCs have information length and blocklength .

In [6], Karimzadeh et al. considered designing optimal CRC polynomials for each input rail of a multi-input CC. In their setup, an information sequence for an encoder needs to be split into subsequences before CRC encoding. In contrast, the entire information sequence in our framework is encoded with a single CRC polynomial. Then the resulting sequence is evenly divided into subsequences, one for each rail. To compare the performance between these two schemes, we design three degree- optimal CRC polynomials, one for each rail, for ZTCC with . The three CRC polynomials jointly maximize the minimum distance of the CRC-ZTCC. For the single-CRC design, we use the single degree- DSO CRC polynomial for the same encoder from Table I. Both CRC-ZTCCs have an information length and blocklength . Fig. 2 shows the performance comparison between these two codes, showing that a single degree- DSO CRC polynomial outperforms three degree- DSO CRC polynomials, one for each rail. This suggests that a single DSO CRC polynomial may suffice to provide a superior protection for each input rail.

Iv TBCC with DSO CRC and Dual Trellis SLVD

The performance of CRC-aided list decoding of ZTCCs relative to the RCU bound is constrained by the termination bits appended to the end of the original message, which are required to bring the trellis back to the all-zero state. TBCCs avoid this overhead by replacing the zero termination condition with the TB condition that the final state of the trellis is the same as the initial state of the trellis [11].

In this section, we apply the SLVD of CRC-TBCCs over the dual trellis. We will discuss how to determine the initial state for the TBCC to ensure that the tail-biting condition is met and demonstrate designs of DSO CRCs for rate TB codes. Decoding complexity and performance are analyzed at the end of this section.

Iv-a List Decoding for TBCC with CRC

There are two primary differences between our development and analysis of list decoding of ZTCCs, as described in Section III, and what is needed for TBCCs. One difference is that since the ZT condition is replaced with the TB condition, the encoder must determine the initial trellis state so that the TB condition is satisfied. The other difference is that SLVD on the dual trellis must be adapted to handle the TB condition.

To satisfy the TB condition, encoding is attempted from every initial state to identify the initial state that satisfies the TB condition. This is required because our recursive encoder cannot simply achieve the TB condition by setting the initial encoder memory to be the final bits of the information sequence.

To adapt SLVD on the dual trellis to handle the TB condition, we propose an efficient way to keep track of the path metrics and find the next path with minimum metric through an additional root node as shown in Fig. 3. The root node connects to all terminating states after forward traversing the dual trellis. The Hamming distance of the branch metric for the branch connecting any state to this root node is zero. This additional root node allows the trellis to end in a single state, so that the basic SLVD approach for a ZTCC may be applied. During SLVD, if the current path does not pass either the CRC or TB check, the minimum value among all remaining path metrics will be selected as the next path to check.

Fig. 3: Dual trellis diagram for rate- TBCC with a root node at the end for encoder with . Solid lines represent paths and dashed lines represent paths.

Iv-B Design of DSO CRCs for High-Rate TBCCs

The design of DSO CRCs for high-rate TBCCs follows the two-phase design algorithm as in [19]. This algorithm is briefly explained below.

Consider a TB trellis of length , where denotes the set of output alphabet, denotes the set of states, and denotes the set of edges described in an ordered triple with and [7]. Assume and let . Define the set of IEEs at state as

(10)

where

(11)

The IEEs at state can be thought of as “building blocks” for an arbitrarily long TB path that starts and ends at the same state .

The first phase is called the collection phase, during which the algorithm collects with output Hamming weight no greater than the threshold over a sufficiently long TB trellis. The second phase is called the search phase, during which the algorithm first reconstructs all TB paths of length and output weight no greater than via concatenation of the IEEs and circular shifting of the resulting path. Then, using these TB paths, the algorithm searches for the degree- DSO CRC polynomial by maximizing the minimum distance of the undetected TB path.

Table II presents the DSO CRC polynomials for TBCCs generated with and . The design assumes a fixed blocklength . TB encoding avoids the rate loss caused by the overhead of the zero termination. Specifically, for a given information length , CRC degree and an encoder, the blocklength for a CRC-TBCC is given by

(12)

yielding a rate

(13)
1-61.2
DSO CRC
0x9
0x7D
0x1CF
0x38F
0x73F
0x9
0x4F
0x173
0x3BF
0x697
1-61.2
TABLE II: DSO CRC Polynomials for rate- TBCC at Blocklength Generated by With and by With

Iv-C Complexity Analysis

In [19], the authors provided the complexity expression for SLVD of CRC-ZTCCs and CRC-TBCCs. Observe that the dual trellis has no more than outgoing branches per state, similar to the trellis of a rate- CC. Thus, we directly apply their complexity expression to the SLVD over the dual trellis.

Fig. 4: The SNR gap to the RCU bound vs. the average complexity of SLVD of CRC-ZTCC codes in Table I and CRC-TBCC codes in Table II for target FER of . Each color represents a specific CRC-aided CC shown in the tables. Markers from top to bottom with the same color correspond to DSO CRC polynomials with = , , and .

As noted in [19], the overall average complexity of the SLVD can be decomposed into three components:

(14)

where denotes the complexity of a standard soft Viterbi (SSV), denotes the complexity of the additional traceback operations required by SLVD, and denotes the average complexity of inserting new elements to maintain an ordered list of path metric differences.

is the complexity of add-compare-select (ACS) operations and the initial traceback operation. For CRC-ZTCCs,

(15)

For CRC-TBCCs, this quantity is given by

(16)

The second component for CRC-ZTCC is given by

(17)

For CRC-TBCCs, is given by

(18)

The third component, which is the same for ZT and TB, is

(19)

where is the expected number of insertions to maintain the sorted list of path metric differences. For CRC-ZTCCs,

(20)

and for CRC-TBCCs,

(21)

In the above expressions, and are two computer-specific constants that characterize implementation-specific differences in the implemented complexity of traceback and list insertion (respectively) as compared to the ACS operations of Viterbi decoding. In this paper, we assume that and use (20) and (21

) to estimate

for CRC-ZTCCs and CRC-TBCCs, respectively.

Fig. 5: FER vs. SNR for various CRC-TBCCs. The TBCC is generated with the encoder . The DSO CRC polynomials of degrees and are 0x9, 0x4F, and 0x3BF, respectively. Values in parenthesis denote information length and blocklength , respectively.
Fig. 6: Expected list rank vs. FER for SLVD of CRC-TBCC with blocklength . The TBCC is generated with . The DSO CRC polynomials of degrees and are 0x9, 0x4F, and 0x3BF.

Fig. 4 shows the trade-off between the SNR gap to the RCU bound and the average decoding complexity at the target FER . The average decoding complexity of SLVD is evaluated according to the aforementioned expressions. We see that for the same ZTCC or TBCC, increasing the CRC degree significantly reduces the gap to the RCU bound, at the cost of a small increase in complexity. However, for the same CRC degree , increasing the overall constraint length dramatically increases the complexity, while achieving a minimal reduction in the SNR gap to the RCU bound.

Iv-D Results, Analysis, and Expected List Rank of SLVD

Fig. 5 shows the FER vs. SNR for three CRC-TBCCs at blocklength . At the target FER of , the SNR gap is reduced to dB for the CRC-TBCC with . Fig. 6 shows the trade-off between the expected list rank and the FER. We see that the expected list rank for achieving the target FER of , implying a low average decoding complexity of SLVD.

V Conclusion

This paper shows list decoding of a rate- CC concatenated with a DSO CRC yields block codes that approach the RCU bound for the BI-AWGN. CRC-TBCCS have FERs within 0.15 dB of RCU bound for FER at blocklength N=128 bits. Adding a bit of CRC can improve FER far more than adding an additional memory element to the CC.

Acknowledgment

The authors thank Dariush Divsalar for helpful discussions on construction of the dual trellis. We thank Ethan Liang and Linfang Wang for guidance and mentorship. Thanks to Mai Vu and Mohammad Karimzadeh for helpful collaboration.

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